Finger using mixed weighting, and its application for demodulation apparatus and method

ABSTRACT

The present invention relates to a finger using mixed-rate weighting in Smart Antenna System, and an apparatus and method for Demodulating signals using such a finger. The present invention is useful in a wireless communication network having a reverse pilot channel. Further, by using such a finger, the present invention provides a demodulation apparatus and method for making high-speed broadband communications available in a smart antenna system. In such 3-G wireless communications where both traffic signals and pilot signals are transmitted from a terminal, the present invention calculates optimized weight vectors using the pilot signal and the calculated weight vectors are adapted to each traffic signal with a symbol-rate weight.

This is a continuation of PCT/KR02/01945 filed Oct. 18, 2002 and published in English.

DESCRIPTION

1. Technical Field

This invention relates to a demodulation technique performing a signal reception in mobile communication environments, e.g., Code Division Multiple Access (CDMA)-type mobile communication, etc. More specifically, this invention relates to a finger that is applicable to smart antenna system with mixed weighting (which means that symbol-rate and chip-rate weighting is mixed), a demodulation apparatus and method that applies the finger, and a computer-readable recording medium for recording a program that embodies the method.

2. Background Art

The importance of smart antenna system is widely recognized as a tool for efficiently increasing the capacity of mobile communication system. In general, it has been known that the smart antenna system enhances the performance of wireless communication system through a spatially selective reception, which causes the interfering signals to be reduced or resolved.

In conventional cases, the weighting information needed in smart antenna system is obtained from the traffic channel in reverse link. The intrinsic characteristic of the traffic channel that the integration interval for despreading procedure cannot be taken long enough, however, the information cannot help being deteriorated.

In order to resolve this problem, there was a Korean Patent No. 239177 registered on Oct. 19^(th) of 1999 entitled, “Receiving Apparatus and Method of Smart Antenna using Pilot Signals in CDMA Mobile Telecommunication System.” In the Korean patent 239177, the signal at each antenna element is multiplied by an adaptive weight and combined to produce array output. The output is despreaded with the PN code and properly filtered. In order to produce the reference signal, however, the filtered signal is multiplied again by the same PN code. The technique disclosed in the patent 239177 is based on error signal produced from the difference between the array output and the reference signal. The adaptive procedure produces the weights to be multiplied by the received signals at the multiple numbers of antenna elements by minimizing the error signal by means of well-known technique, Least Mean Square algorithm.

The problem in this method, however, is in executing the LMS algorithm which essentially needs the reference signal for producing the difference to be minimized at each adaptation step. In fact, the procedure of multiplying the PN code to the despreaded received signal is needed only to produce the reference signal. It is absolutely irrelevant to the reception or demodulation procedure itself. The procedure of producing the reference signal must cause additional delays and errors as well as the complexity due to PN-code multiplication.

As another technique, there is a Korean patent application 1999-28020 which has been published on Feb. 5^(th) of 2001, entitled “CDMA Signal Demodulator for an adaptive smart antenna system.” In this invention, CDMA signal demodulator in the adaptive smart antenna system consists of a searcher bank for PN-code acquisition, a finger bank which produces accurate timing information, a correlator bank which produces the despreaded data, a beam-forming parameter computer which produces the weights to be multiplied to received signal, a beam-forming multiplier which produces the array output by multiplying the weights to the received signal, and a multipath combiner which aligns the despreaded data in time domain.

The problem in this technique is that it does not provide how each block (or, equivalently, bank) co-operates and interfaces to each other. One practical phenomenon caused by that defect is the initial PN-code acquisition cannot be achieved. In order for the smart antenna system shown in the Korean patent application 1999-28020 to work as properly as claimed, it should be assumed that all the timing information needed at each block must be provided externally, which is not true in real situations. For example, both initial PN-code acquisition and multipath searching should somehow be achieved apriori at the beginning stage, which is never realistic in practical situations, for the correlator bank to work properly. More specifically, the technique disclosed in the Korean patent application 1999-28020 fails to provide how the timing information is provided from the searcher bank to the correlator bank and the beam-forming parameter computer such that the correlation for despreading the received signal and computing the weights at a proper time cannot be achieved. Also, without specifying the detailed method of PN-code acquisition, multipath combining, which is essential in CDMA receiver, can never be achieved as well.

Therefore, the system shown in the Korean patent application 1999-28020 must start with inaccurate timing information at the beginning stage, which results in extremely adverse reliability. In addition, inaccurate timing information results in tremendously slow convergence in adapting the weights even if it can converge. Mostly, it does not converge at all.

Another technique is disclosed in a Korean patent application 1999-30463 published on Feb. 15^(th) of 2001, entitled “Smart Antenna System having a beam-former and an adaptive equalization combiner for multipath signals.” The main part of this technique is that a beam-forming can be achieved through an adaptive beam-forming algorithm instead of selection diversity through the searcher bank.

In this technique as well as in the previous ones, there is no explanation about how the timing information is obtained. More specifically, it is assumed in this technique that the searching is perfectly obtained apriori at the beginning stage, i.e., stage before the despreading procedure for the chip-level weighting, which is never true in real situations. As in the previous case, i.e., 1999-28020, the inaccurate timing information due to the lack of specified searching technique must cause very slow converge in the adaptation of weights even if the procedure does not diverge. The slow convergence leads to a serious degradation in performance of smart antenna system.

In addition, this technique fails to disclose for any normal people with common knowledge to understand how the adaptive beam-forming algorithm searches for the weights.

DISCLOSURE OF INVENTION

This invention has been proposed to resolve the problems in the conventional techniques discussed above. The objective of this invention is to provide a finger with a main emphasis on the application to a smart antenna system for tracking of each user and providing high speed wide-band communication by weighting received data carried in traffic channels in mixed-rate (which means symbol-rate and chip-rate is mixed) with the weights computed from pilot channel signal in the reverse link.

This invention also provides a demodulation apparatus of a smart antenna system using the fingers operating in mixed-rate for tracking of each user and achieving high speed wide-band communication by weighting the received data carried in traffic channels with the weights computed from pilot channel signal in the reverse link.

This invention also provides a demodulation method of a smart antenna system using the fingers operating in mixed-rate for tracking of each user and achieving high speed wide-band communication by weighting the received data carried in traffic channels with the weights computed from pilot channel signal in the reverse link.

This invention also provides a computer-readable recording medium for recording a program that embodies the method using fingers operating in mixed-rate for tracking of each user and achieving high speed wide-band communication by weighting the received data carried in traffic channels with the weights computed from pilot channel signal in the reverse link.

Those who are skilled in the art of the present invention will easily recognize another purposes and advantages of the invention from the drawings, detailed description of the invention, and claims.

In order to satisfy the objectives and to resolve the problems discussed above, a finger operating in mixed-rate that is provided by this invention, comprises: a descrambling means that descrambles received signals by multiplying a PN-code with the received signals using frame timing information; a pilot signal generating means that produces a pilot signal that is to be used as input of a weight vector computing means to compute a weight vector, by using a descrambled signal from the descrambling means, and finds out estimation value for delayed phase of each traffic channel; the weight vector computing means that produces the weight vector by using signals from the descrambling means and the pilot signal generating means; a general weighting means for producing a general weighted signal, by compensating phase delay of the base-band received signal with the weight vector; a pilot phase estimation means that produces phase compensation signal to compensate phase delay of each channel by using the weight vector and the pilot signal; a Walsh despreading means for providing received data for each of traffic channels, by using outputs of the general weighting means, the PN-code and corresponding Walsh codes; and a channel compensation means that compensates phase distortion caused by the phase delay to each output of the Walsh despreading means by using output of the pilot phase estimation means.

Also, the finger further comprises a tracking means for producing frame tracking information for compensating small changes in path delay.

In order to achieve above-mentioned objectives, there is provided a demodulation apparatus that uses fingers operating in mixed-rate for mobile communication system, comprising: an analog-to-digital converter (ADC) for converting analog signal, which has been frequency-down converted to base-band, to corresponding digital signal through oversampling procedure; a searcher for transmitting the searcher-energy (or, equivalently, the correlation energy) that exceeds preset threshold value to lock detector while the searcher-energy is computed through correlation procedure between output of the ADC and the PN-code corresponding to the pilot channel; a lock detector for generating signals needed for accurate frame synchronization such as the frame reset (f_reset), the frame timing (f_timing), the frame death (f_death) information using the correlation energy provided from the searcher; and at least one finger wherein the traffic channel signals are weighted in the mixed-rate with the weights which are obtained from the received data in the pilot channel of the reverse link.

The finger of the demodulation apparatus in accordance with this invention comprises: a descrambling means that descrambles base-band received signal by using frame time information; a pilot signal generating means that produces the pilot signal from the descrambling means and finds out estimation value for delayed phase of each traffic channel; a weight vector computing means that produces the weight vector using signals from the descrambling means and the pilot signal generating means; a general weighting means for producing the array output using the weight vector and the received signal; a pilot estimation means that produces phase compensation signal to compensate phase delay of each channel using the weight vector and the pilot signal; a Walsh despreading means that produces received data for each of the traffic channels, by using outputs of the general weighting means, the PN-code and corresponding Walsh codes; a channel compensation means that compensates phase distortion caused by the phase delay to each output of the Walsh despreading means using output of the pilot weighting means and traffic channels weighting means.

The finger of the demodulation apparatus further comprises a tracking means for producing the frame tracking information produced from difference between two energies which are obtained by integrating results of the early and late descrambling wherein the first and second synch time information are used, respectively, in order to produce frame tracking information for compensating small changes in path delay.

Also, the searcher that is applied in the demodulation apparatus comprises: a received signal processing means for achieving envelope detection of the received data such that the correlation energy to be obtained at each antenna channel; an adding means for summing up the correlation energies at each of antenna channels obtained from the received signal processing means; and an output means for generating result of the adding means as final output of non-coherent detection.

In accordance with one aspect of the present invention, there is provided a demodulation method using a finger that operates in mixed-rate for mobile communication system, comprising: a first step of descrambling received signal by multiplying a PN-code with a received signal using frame timing information (f_timing); a second step of generating the pilot signal obtained by integrating the descrambled signal in order to use it for computing the weight vector; a third step of computing the weight vector by using the descrambled data and the pilot signal; a fourth step of generating the array output by summing up the results of multiplication between the weight vector and the received signal in such a way that inter-element phase difference be compensated; a fifth step of generating the phase compensating signal to compensate phase delay of channel by multiplying the weight vector with the pilot signal; a sixth step of generating received data for each of the traffic channels by using outputs of the general weighting step, the PN-code, and corresponding Walsh codes; and a seventh step of compensating the phase distortion due to the channel delay by using the phase compensation signal to weighted traffic signal.

In order to achieve above-mentioned objectives, this invention also provides a computer-readable recording medium for recording a program that embodies the method using fingers operating in mixed-rate comprising: a first function of descrambling received signal by multiplying a PN-code with a received signal using frame timing information (f_timing); a second function of generating a pilot signal obtained by integrating a descrambled signal in order to use it for computing weights; a third function of computing a weight vector using the descrambled signal and the pilot signal; a fourth function of generating the array output by summing up the results of multiplication between the weight vector and the received signal in such a way that inter-element phase difference be compensated; a fifth function of generating the phase compensation signal to compensate phase delay of channel by multiplying the weight vector with the pilot signal; a sixth function of generating received data for each of the traffic channels by using outputs of the general weighting step, the PN-code, and corresponding Walsh codes; and a seventh function of compensating the phase distortion due to the channel delay by using the phase compensation signal to weighted traffic signal.

BRIEF DESCRIPTION OF DRAWINGS

The above and other objects and features of the present invention will become apparent from the following description of the preferred embodiments given in conjunction with the accompanying drawings, in which:

FIG. 1 illustrates one desirable example of a block-diagram of a finger operating in mixed-rate, according to the present invention.

FIG. 2 illustrates one example of a block-diagram of a demodulation apparatus, according to the present invention, that is equipped with the fingers shown in FIG. 1.

FIG. 3 describes concept of technology, which is referred to as “phase diversity technology,” used in a searcher and a tracker disclosed in this invention.

FIG. 4 illustrates performance of the phase diversity technology when S_(l,k)=50 and σ²=1000. It can be observed that distribution of energy (Z_(l,k)) is more concentrated as number of antenna is increased.

FIG. 5 illustrates performance of the phase diversity technology when S_(l,k)=0 (no desired signal) and σ²=1000. It can be observed that distribution of energy (Z_(l,k)) is more concentrated as number of antenna is increased.

FIG. 6 illustrates an example of application of the phase diversity to the searcher operating in reverse link of a mobile communication system.

FIG. 7 illustrates theoretical performance of detection probability (P_(D)) and false alarm probability (P_(F)) when processing gain (PG), i.e., period for the pilot channel integration, is 64 and number of interferers is 50.

FIG. 8 illustrates simulation performance of detection probability and false alarm probability when processing gain (PG), i.e., period for the pilot channel integration, is 64 and number of interferers is 50.

FIG. 9 illustrates theoretical values for P_(F) and P_(D) when number of antenna elements is one.

FIG. 10 illustrates simulation values for P_(F) and P_(D) when number of antenna elements is one.

FIG. 11 illustrates a flow-chart of a desirable example of the demodulation method using the finger operating in mixed-rate, according to the present invention.

FIG. 12 illustrates how much delay is encountered in procedure of mixed-rate weighting itself in FIG. 11.

BEST MODE FOR CARRYING OUT THE INVENTION

Objectives, characteristics, and merits of this invention described above will be more clarified through explanations given in this section. In explaining this invention, details of conventional techniques that are used in common with this invention have been excluded in this document because, otherwise, it may confuse originalities disclosed only in this invention. This section presents desirable examples applying techniques disclosed in this invention together with figures.

FIG. 1 illustrates one desirable example of a block-diagram of the finger operating in mixed-rate disclosed in this invention. In FIG. 1, 110, 120, 130, 140, 150, 160, 170, and 180 represent descrambling part, pilot signal generating part, weight vector computing part, general weighting part, pilot phase estimation part, Walsh despreading part, channel compensating part, and tracking part, respectively.

As illustrated in figures, the finger according to one example of this invention is composed of following parts: a descrambling part (110) that descrambles received signal by multiplying the PN-code with the received signal in digital-state (which means received signal transformed into base-band from each antenna element and hereinafter, will be referred to “received signal”) using the frame timing information provided from outside the finger; a pilot signal generating part (120) that generates the pilot signal to be used as input of the weight vector computing part by integrating output of the descrambling part (110); a weight vector (beam-forming parameter) computing part (130) that computes the weight vector by using the descrambled signal from the descrambling part (110) and pilot signal provided from pilot signal generating part, respectively; a general weighting part (140) that produces the array output by multiplying the received signal with the weight vector and summing up results of the multiplications in such a way that the inter-element phase difference between antenna elements to be compensated; a pilot phase estimation part (150) that produces phase compensation signal to compensate phase delay of channel by multiplying the weight vector from the weight vector computing part (130) with the pilot signal.

In addition, the finger presented in this invention is also composed of following parts: a Walsh despreading part (160) that separates the array output into each of traffic channel signals by multiplying the PN-code to the array output coming from the general weighting part (140) and multiplying above result with the Walsh code assigned at each of traffic channels; a channel compensation part (170) for compensating phase distortion caused by the phase delay to each output of the Walsh despreading part (160) by using output of the pilot phase estimation part (150); Furthermore, this invention also provides the tracking part (180) inside the finger operating in mixed-rate that generates the frame tracking information (f_trk) in order to compensate small change in path delay such that fine-tuning of tracking can be achieved in a given the finger.

The weight vector computing part (130) provides the beam-forming parameter, i.e., the weight vector, by processing the received signal in accordance with preset arithmetic procedure. The weight vector is complex-valued vector of which real and imaginary part will be denoted in this document by Weight_I and Weight_Q, respectively. Finger death signal (f_death) is generated in the lock detector in conjunction with the searcher when PN-code acquisition at a given finger is lost. For re-locking of PN-code acquisition when the finger death signal (f_death) occur, f_reset is generated from the lock-detector and the weight vector computing part (130) is in turn reset such that the weight vector computing part (130) is started from initial stage.

When the pilot signal is multiplied by the weight vector, it is desirable to weight the pilot signal through calculation of phase delay, which is delay between reference antenna and each antenna element.

As mentioned earlier, it is extremely important to provide exact timing information, i.e., synchronization between the received signal and local PN-code, for accurate demodulation of CDMA data. Therefore, the tracking part (180) generates the frame tracking information (f_trk) by observing energy difference between early and late descrambling of received signal and local PN-code. The difference in time lag of early and late correlation is preset with proper amount. Early and late time information will be denoted as first and second sync time information, respectively, in this document.

In the tracking part (180), it is desirable that the first synch time information is to be 0.2 or 0.5 chips duration earlier than the frame timing information (f_timing) while the second synch time information is to be 0.2 or 0.5 chip later.

In the tracking part (180), the timing information is produced from difference between two energies which are obtained by integrating results of the early and late descrambling wherein the first and second synch time information are used, respectively. Or, in the tracking part, the energies corresponding too early and late descrambling can also be generated by squaring weighted sums between the weight vector and integration of the descrambled signal obtained through the early and late descrambling procedure, respectively. Another method in the tracking part is that the energies corresponding too early and late descrambling can also be generated by squaring integration of weighted sums between the weight vector and the descrambled signal obtained through the early and late descrambling procedure, respectively.

For obtaining the frame tracking information (f_trk) in the tracking part (180), some additional processing may also be included in addition to computing the difference of energies of early and late correlations such as low pass filtering of the energy difference.

In a desirable example of this invention, DLL (Digital Lock Loop) has been adopted at each the finger for fine-tracking to countermeasure the small changes in path delay during communication. Through many computer simulations, it has been found that the frame time information (f_timing) is to be changed by ⅓-⅛ chip earlier or later than current value.

For easy explanation of techniques disclosed by this invention, we take demodulation apparatus of CDMA2000 1X as an example of applying the finger.

Referring to FIG. 1 that shows one desirable example of the finger structure, the descrambling part (110) performs complex descrambling the received signal of which In-phase and Quadrature-phase component has been respectively scrambled with corresponding PN-code by correlating it with the PN-code using frame timing information (f_timing) provided from the lock detector shown in FIG. 2A.

The pilot signal generating part (120) retrieves the pilot signal in order to compensate phase delay of channel by integrating the descrambled data and output signal from the pilot signal generating part is fed into the weight vector computing part. Output of the pilot signal generating part and the descrambling part will be denoted as y-vector and x-vector, respectively, in this document. Y-vector is obtained from integration of x-vector and one of x-vector during integration period is fed into the weight vector computing part. Depending on the arithmetic procedure of computing the weight vector in the weight vector computing part, only one of x- or y-vector can be used instead of both of them. Furthermore, the descrambling part (110) and the pilot signal generating part (120) might also be unified as a single part such that the two operations can be achieved in the single part.

The weight vector computing part (130) produces the weight vector (Weight_I, Weight_Q) using the x-vector and y-vector provided from the descrambling part (110) and pilot integrating part (120), respectively. In addition, the weight vector computing part (130) can also include weight vector initializing part as well. Furthermore, the weight vector computing part (130) can also be equipped with additional part of receiving the frame reset signal (f_reset) from the lock detector (Refer to FIG. 2) in order to reset the weight vector into initial state. Also, depending on the arithmetic procedure of computing the weight vector in the weight vector computing part, only one of x- or y-vector can be used.

The general weighting part (140) generates the array output in the chip-rate by multiplying the received data by the weight vector and summing up results of the multiplications in such a way that the inter-element phase difference between antenna elements to be compensated.

The pilot phase estimation part (150) retrieves the pilot signal that is to be used to compensate the phase distortion due to the path delay by multiplying the pilot signal from the pilot signal generating part (110) with the array output obtained from the general weighting part (140). The pilot phase estimation part (150) also detect power control bit and provides frame energy signal (f_eng) to the lock-detector such that current value of the frame energy be transmitted to the lock detector.

Furthermore, in a desirable example of this invention, the Walsh despreading part (160) comprises following parts: Fundamental channel (which will be referred to as “FCH” for simplicity) despreading part (161) for retrieving data transmitted through the FCH by descrambling the array output through multiplication of the array output with the PN-code and further multiplying result of the descrambling of the array output with the Walsh code corresponding to the FCH of length 16 chips such that symbol rate of resultant data to be reduced by 1/16 chip-rate (76.8 kbps); Dedicated control channel (which will be referred to as DCCH for simplicity) despreading part (163) for retrieving data transmitted through DCCH by descrambling the array output through multiplication of the array output with the PN-code and further multiplying result of the descrambling of the array output the Walsh code corresponding to the DCCH of length 16 chips such that symbol rate of resultant data to be reduced by 1/16 chip-rate (76.8 kbps); Supplemental channel #1 (which will be referred to as SCH#1 for simplicity) despreading part (165) for retrieving data transmitted through SCH#1 by descrambling the array output through multiplication of the array output with the PN-code and further multiplying result of the descrambling of the array output with the Walsh code corresponding to the SCH#1 of length 16, 8, 4, or 2 chips such that symbol rate of resultant data to be reduced by 1/16, ⅛, ¼, or ½ chip-rate (76.8 kbps, 153.6 ksps, 307.2 ksps, or 614.4 ksps); Supplemental channel #2 (which will be referred to as SCH#2 for simplicity) despreading part (167) for retrieving data transmitted through SCH#2 by descrambling the array output through multiplication of the array output with the PN-code and further multiplying result of the descrambling of the array output with the Walsh code corresponding to the SCH#2 of length 16, 8, 4, or 2 chips such that symbol rate of resultant data to be reduced by 1/16, ⅛, ¼, or ½ chip-rate (76.8 kbps, 153.6 ksps, 307.2 ksps, or 614.4 ksps). In the Walsh despreading part, procedure of the descrambling and that of correlating with corresponding Walsh code can be performed in a single procedure using multiplication of the Walsh code and PN-code on chip-by-chip basis.

The channel compensating part (170) compensates the phase distortion due to the path delay associated with each of traffic channels separately such that the channel compensating part (170) consists of plural the channel compensating parts. For example, there are four the channel compensating parts (171), (173), (175), and (177) in case of CDMA2000 1X system.

The tracking part (180) which provides exact chip synchronization through the fine-tuning of PN-code acquisition comprises following parts: complex descrambling part 1 (181) for multiplying the received signal with the PN-code of ½ chip advanced time to f_timing (this descrambling part will be denoted as “early descrambling part” in this document); complex descrambling part 2 (183) for multiplying the received signal with the PN-code of ½ chip retarded time to f_timing (this descrambling part will be denoted as “late descrambling part” in this document); energy estimation parts (185, 187) for providing the correlation energies by integrating results of the complex descrambling part 1 and complex descrambling part 2 (181, 183), respectively; and tracking information (f_trk) generating part (189) for providing the tracking information (f_trk) by comparing magnitudes of results of the energy estimation parts (185, 187). In the descrambling parts, the advanced and retarded time to the f_timing in early and late descrambling part, respectively, can be some other values than ½. In general, it has been found that early and late time can be selected in range of 0.2 to 0.5.

The energy estimation part (185, 187) is needed for the fine-tuning of chip synchronization of the local PN-code and the received signal. Integration value of energy level between the received signal and the local PN-code has maximum value in case of perfect chip synchronization.

In the tracking information (f_trk) generating part (189), the tracking information (f_trk) is obtained by comparing the integration values provided from the correlation energy generating parts (185, 187) which are associated with the early and late descrambling part, respectively. Voltage controlled oscillator (VCO) can be used to produce the tracking information (f_trk).

As described above in detail, the finger of CDMA receiver with a main emphasis on the application to smart antenna system makes it possible to track each user and provide high speed wide-band communication by weighting received data carried in the traffic channels in chip-rate with the weights computed from the pilot channel in the reverse link.

Although there are four the fingers assigned for each user in the demodulation apparatus of the smart antenna system in a desirable example in this document, it is clear to any normal people with common knowledge that number of the fingers assigned to each user can be set to any proper number in a given circumstance.

FIG. 2 illustrates an example of applications of the finger disclosed in this invention shown in FIG. 1. It is clear that the finger disclosed in this invention can be applied to the demodulation apparatus operating in any other kind of communication environments (such as WCDMA system instead of CDMA2000 1X system). The demodulation apparatus shown in FIG. 2 comprises the ADC (210), the searcher (220), the lock detector (230), the fingers (240 a-240 d), and received signal processing part (250).

As shown in FIG. 2, the demodulation apparatus applying the finger operating in mixed-rate comprises the analog-to-digital converter (ADC) for generating the received signal through procedure of oversampling received analog signal after the frequency-down conversion and the searcher (220) for transmitting the searcher-energy (or, equivalently, the correlation energy) that exceeds preset threshold value to lock detector while the searcher-energy is computed through correlation procedure between output of the ADC and the PN-code corresponding to the pilot channel.

In addition, the demodulation apparatus applying the finger operating in chip-rate also comprises the lock detector (230) for generating signals needed for accurate frame synchronization such as the frame reset (f_reset), the frame timing (f_timing), the frame death (f_death) information using the correlation energy provided from the searcher. As described already in previous explanations of FIG. 1, the demodulation apparatus comprises at least one the finger (240 a-240 d), which also comprises the descrambling part (110), the pilot signal generating part (120), the weight vector computing part (130), the general weighting part (140), the pilot phase estimation part (150), the Walsh despreading part (160), the channel compensating part (170), and the tracking part (180) (which is also denoted as “tracker” in this document), and the received signal processing part (250) which performs conventional functions of receiving apparatus such as signal combiner, de-interleaver, soft-decision performer, Viterbi decoder, CRC (cyclic redundancy code) checker, turbo decoder, and/or other kinds of conventional signal receiving, estimating, and/or detecting parts.

As shown in FIG. 2C, the received signal processing part (250) comprises the signal combiner for combining each of the traffic signals fed from plural the fingers, de-interleaver for rearranging received data back to their original order, soft decision performer for providing the soft decision of the de-interleaved data, the Viterbi decoder for decoding convolutionally encoded data, CRC checker for detecting frame error, etc, of which structure and functions are so conventional to people with knowledge of this field that detailed explanations are omitted in this document.

Furthermore, technology that can appropriately be applied to enhance performance of the searcher (220) without computing the weights has already been submitted as a patent (as of 20971 in Korea) dated as on Apr. 18, 2001.

From here after, more detailed explanations about the finger are provided using related figures.

FIG. 3 illustrates a conceptual block diagram for explaining concept of the phase diversity technology that is applied to the searcher (220). For easier explanation, let's take an example from demodulation procedure of received data at n-th antenna element. The phase diversity that has been applied to the finger disclosed in this invention is explained in more detail from here using related figures that have been obtained through various computer simulations. Suppose there are M waves impinging upon the smart antenna system with distinct incident angles. This corresponds to the case of M users transmitting signals to the smart antenna system assuming no multipath. However, in multipath environment, the number of users is a lot less than M. In either case, the phase difference between two antenna elements in the smart antenna system due to a signal propagated through a single path, say, l-th path, can be written as φ(θ_(l), d), a function of the incident angle θ_(l) and the element separation d. Therefore, Phase difference=φ(θ_(l) , d)  [EQUATION 1]

Suppose the l-th path carries desired signal, and the first antenna element is reference element. Then, the desired and undesired part of l- and Q-component of the received signal at the k-th branch of the n-th antenna element, denoted by I_(n,k) and Q_(n,k), respectively, can be written as

$\begin{matrix} \begin{matrix} {I_{n,k} = {{S_{l,k}\mspace{14mu}{\cos\left\lbrack {\phi_{l} + {\left( {n - 1} \right){\varphi\left( {\theta_{l},d} \right)}}} \right\rbrack}} +}} \\ {\sum\limits_{{m = 1},{m \neq l}}^{M}{S_{m,k}\mspace{14mu}{\cos\left\lbrack {\phi_{m} + {\left( {n - 1} \right){\varphi\left( {\theta_{m},d} \right)}}} \right\rbrack}}} \end{matrix} & \left\lbrack {{EQUATION}\mspace{20mu} 2} \right\rbrack \\ \begin{matrix} {Q_{n,k} = {{S_{l,k}\mspace{14mu}{\sin\left\lbrack {\phi_{l} + {\left( {n - 1} \right){\varphi\left( {\theta_{l},d} \right)}}} \right\rbrack}} +}} \\ {\sum\limits_{{m = 1},{m \neq l}}^{M}{S_{m,k}\mspace{14mu}{\sin\left\lbrack {\phi_{m} + {\left( {n - 1} \right){\varphi\left( {\theta_{m},d} \right)}}} \right\rbrack}}} \end{matrix} & \left\lbrack {{EQUATION}\mspace{20mu} 3} \right\rbrack \end{matrix}$

where θ_(m) is carrier phase delay associated with the m-th path, and S_(m,k) is the amplitude of the received signal at the k-th branch of the reference antenna element propagated through the m-th path. Note that the first terms of equation (2) and (3) are the desired signals, and the second terms are the interferences since the l-th path carries the desired signal. The noise terms are ignored for the sake of simplicity. If incident angles {θ_(m)} are assumed to be mutually independent random variables with uniform distribution, then, for sufficiently large M, the interfering terms, i.e., the second terms of equation (2) and (3), are mutually independent Gaussian random variables. Then, equation (2) and (3) can be rewritten as I _(n,k) =G[S _(l,k)cos(Θ_(n,l)),σ²]  [EQUATION 4] Q _(n,k) =G[S _(l,k)sin(Θ_(n,l)), σ²]  [EQUATION 5]

where G[μ,σ²] denotes a Gaussian random variable with mean μ and variance σ² where the variance is determined by the sum of the interferers' power measured at receiving side, and Θ_(n,l)=φ_(l)+(n−1)φ(θ_(l), d).

The correlation energy is obtained from squared sum of l- and Q-components for the non-coherent envelope detection. Denoting the correlation energy associated with the k-th branch by Z_(k), it is claimed in the “Phase diversity technology” (a patent in pending as of 20971 in Korea dated as on Apr. 18, 2001) that each of the correlation energy should be obtained from the sum of all the corresponding l- and Q-components obtained from each antenna element, i.e.,

$\begin{matrix} {{Z_{k} = {{\sum\limits_{n = 1}^{N}{\left\lbrack {I_{n,k}^{2} + Q_{n,k}^{2}} \right\rbrack\mspace{85mu}{for}\mspace{14mu} k}} = 1}},2,\ldots\mspace{11mu},K} & \left\lbrack {{EQUATION}\mspace{20mu} 6} \right\rbrack \end{matrix}$

Probability density function (PDF) of the correlation energy Z_(k) can be written as

$\begin{matrix} \begin{matrix} {{p_{Z_{k}}(\alpha)} = \frac{\left( {{\alpha/\sigma^{2}}b_{k}} \right)^{{({N - 1})}/2}}{2\sigma^{2}}} & {{{for}\mspace{14mu}\alpha} \geq 0} \\ {{{\mathbb{e}}^{{- \frac{1}{2}}{({b_{k} + {\alpha/\sigma^{2}}})}}{I_{N - 1}\left( \sqrt{\frac{b_{k}\alpha}{\sigma^{2}}} \right)}},} & \; \\ {{= 0},} & {{{for}\mspace{14mu}\alpha} < 0} \end{matrix} & \left\lbrack {{EQUATION}\mspace{20mu} 7} \right\rbrack \end{matrix}$

where the non-centrality parameter

$b_{k} = {N\frac{\; S_{k}^{2}}{\sigma^{2}}}$ and I_(N−1)(●) is the modified Bessel function of the first kind with order N−1. Note that when S_(k)=0, b_(k) becomes zero. This means that when the amplitude of the desired signal is zero at the k-th branch. Therefore, when there is no the desired signal at the k-th branch, the correlation energy Z_(k) is a central chi-squared random variable. For this case, the PDF of the correlation energy Z_(k) becomes,

$\begin{matrix} {{p_{Z_{k}}(\alpha)} = {\frac{1}{\left( \sigma^{2} \right)^{N}2^{N}{\Gamma(N)}}\alpha^{({N - 1})}{\mathbb{e}}^{{{- \alpha}/2}\sigma^{2}}}} & \left\lbrack {{EQUATION}\mspace{20mu} 8} \right\rbrack \end{matrix}$

where Γ(●) denotes Gamma function.

The mean of the central chi-square random variable is 2Nσ² and its variance is 4Nσ⁴. For the case of non-central Chi-square, the mean is N(2σ²+S²) and the variance is 4Nσ²(σ²+S²). Both the mean and variance of the correlation energy Z_(k) increase linearly as the number of antenna elements increases. This indicates that performance of the non-coherent detection improves linearly as the number of antenna elements in the smart antenna system increases. Consequently, the phase diversity technique, through the correlation energy Z_(k), increases the signal-to-interference ratio (SIR) by nearly N-times where N is the number of antenna elements in the smart antenna system. It is important that there is no the weight computation involved in achieving the phase diversity gain.

FIG. 4 and FIG. 5 show the probability distribution of correlation energy Z_(k) as the number of antenna elements varies from 1 to 4. FIG. 4 shows the case of S_(k)=50, σ²=1000, which means there exists the desired signal; whereas FIG. 5 shows the case of S_(k)=0, σ²=1000, which means there is no the desired signal present. FIG. 6 illustrates a block diagram of the searcher applied in an example of CDMA system incorporating the phase diversity technique. In FIG. 6, P_(l)(t−τ) and P_(Q)(t−τ) denote the l- and Q-component, respectively, of the PN-code corresponding to the desired signal impinging upon the smart antenna system through the l-th path. Objective of the PN-code acquisition is to find the timing information, more specifically, value for time lag τ in P_(l)(t−τ) and P_(Q)(t−τ) which provides peak value in the correlation. As subscript k is deleted, the correlation energy Z can be rewritten as

$\begin{matrix} {Z = {\sum\limits_{n = 1}^{N}{\left\lbrack {I_{n}^{2} + Q_{n}^{2}} \right\rbrack.}}} & \left\lbrack {{EQUATION}\mspace{20mu} 9} \right\rbrack \end{matrix}$

Considering following two hypotheses;

H₁: acquisition is achieved

H₀: acquisition is not achieved

then, conditional probabilities under these hypotheses are

$\begin{matrix} {{{p_{Z}\left( \alpha \middle| H_{0} \right)} = {\frac{1}{\left( \sigma^{2} \right)^{N}2^{N}{\Gamma(N)}}\alpha^{({N - 1})}{\mathbb{e}}^{{{- \alpha}/2}\sigma^{2}}}},} & \left\lbrack {{EQUATION}\mspace{20mu} 10} \right\rbrack \\ \begin{matrix} {{p_{Z}\left( \alpha \middle| H_{1} \right)} = {\frac{\left( {{\alpha/\sigma^{2}}b} \right)^{{({N - 1})}/2}}{2\sigma^{2}}{\mathbb{e}}^{{- \frac{1}{2}}{({b + {\alpha/\sigma^{2}}})}}}} \\ {{I_{N - 1}\left( \sqrt{\frac{b\;\alpha}{\sigma^{2}}} \right)},} \end{matrix} & \left\lbrack {{EQUATION}\mspace{20mu} 11} \right\rbrack \end{matrix}$

where σ²=2TM in (10), σ²=2T(M−1) in (11), and b=2TM/(M−0.5) with T being the integration interval in computing the correlation energy. From (10) and (11), probabilities of detection and false alarm in a single synchronization test can respectively be given as

$\begin{matrix} \begin{matrix} {P_{F} = {{\Pr\left\{ {Z > \beta_{T}} \middle| H_{0} \right\}\mspace{14mu}{with}\mspace{14mu}\sigma^{2}} = {2T\; M}}} \\ {= {\int_{\beta_{T}}^{\infty}{\frac{1}{\left( \sigma^{2} \right)^{N}2^{N}{\Gamma(N)}}\alpha^{({N - 1})}{\mathbb{e}}^{{{- \alpha}/2}\sigma^{2}}\ {\mathbb{d}\alpha}}}} \end{matrix} & \left\lbrack {{EQUATION}\mspace{20mu} 12} \right\rbrack \\ \begin{matrix} {P_{D} = {{\Pr\left\{ {Z > \beta_{T}} \middle| H_{1} \right\}\mspace{14mu}{with}\mspace{14mu}\sigma^{2}} = {2T\;\left( {M - 1} \right)}}} \\ {= {\int_{\beta_{T}}^{\infty}{\frac{\left( {{\alpha/\sigma^{2}}b} \right)^{{({N - 1})}/2}}{2\sigma^{2}}{\mathbb{e}}^{{- \frac{1}{2}}{({b + {\alpha/\sigma^{2}}})}}}}} \\ {{I_{N - 1}\left( \sqrt{\frac{b\;\alpha}{\sigma^{2}}} \right)}{{\mathbb{d}\alpha}.}} \end{matrix} & \left\lbrack {{EQUATION}\mspace{20mu} 13} \right\rbrack \end{matrix}$

Solving equation (12) and (13) for β_(T), theoretical values for the detection probability and false alarm probability can be obtained. FIG. 7 shows the theoretical values of the detection and false alarm probabilities obtained from equation (12) and (13), and FIG. 8 shows corresponding results for real situation obtained from Monte Carlo simulation. In FIG. 7 and FIG. 8, the integration interval T has been set in such a way that the number of chips in the integration interval becomes 64. It means that processing gain of 64 has been exploited during the searching procedure. Number of the interferers has been set to be 50.

FIGS. 9 and 10 show the detection probability and false alarm probability for a single antenna system as a function of number of the interferers. It is worthwhile to note that the performance of a searcher in a given CDMA receiver is drastically enhanced by the phase diversity technology. For instance, as shown in FIG. 8, the smart antenna system with 4 antenna elements incorporating the phase diversity technique can tolerate 50 of the interferers while conventional one-antenna system can tolerate only 20 of the interfering users to maintain comparable searching performance. This implies that communication capacity is increased by nearly 2.5 times for the PN-code acquisition. This improvement is due to 4 dB gain in SIR through the phase diversity technique in the smart antenna system of 4 antenna elements.

The main contribution of the phase diversity technology is that the smart antenna system can be made to outperform normal one-antenna systems even from initial stage when optimal the weight vector is not available.

The demodulation apparatus with above-described structures and functions makes it possible in the smart antenna system that each user be tracked accurately and high speed wide-band communication be provided by weighting the received data carried in the traffic channels in mixed-rate with the weights computed from the pilot channel in the reverse link.

The demodulation apparatus disclosed is for each user's channel card. As an example, the channel card with four the finger at each user's channel card has been introduced in this document. However, it is clear to any people of this field that number of the fingers to be assigned at each user can be set with any proper selection depending on given signal environment and/or convenience.

FIG. 11 illustrates a flow chart of the demodulation method using the finger in which the received signal are weighted in the mixed-rate as described in this invention. FIG. 12 illustrates how much processing delay is encountered in the demodulation procedure adopting the finger that operates in the mixed-rate.

According to FIG. 11, the demodulation method disclosed in this invention can be explained as follows: the received signal is descrambled in the complex descrambler (501) using the frame timing information (f_timing) by multiplying the received signal with the PN-code. Then, the pilot signal is produced by integrating (503) the descrambled data in order to use as input signal for computing the weight vector. The beam-forming parameter, i.e., the weight vector, is computed (505) from the descrambled received signal and the pilot signal. Computing time required for obtaining the weight vector is dependent upon processor and algorithm used in the weight vector computing part, although it has been written as being a single snapshot period in example shown in this invention.

After the received signal is multiplied by the weight vector in the general weighting part, results of multiplications are summed up to produce each traffic channel signal. When the pilot signal is multiplied by the weight vector, it is desirable to weight the pilot signal through calculation of phase delay, which is delay between reference antenna and each antenna element.

Then, each signal at traffic channels is retrieved separately (509) by correlating the array output with each of Walsh codes assigned to each corresponding channel. Also, the weighted pilot signal for compensating the phase distortion is applied to each of traffic channels separately to produce phase-compensated data (513).

In FIG. 12, period written as x1, x2, . . . , x8 denotes the integration period for descrambling the received signal in the pilot signal generating part (120). Results of the integration period are denoted as y1, y2, . . . , y7, respectively.

The weight vector computing part (130) receives two inputs, one is the x_vector and the other is y_vector. As the y_vector is integration result of the x_vector, y1 in FIG. 12 is available after the integration of corresponding x1 is completed. Similarly, as weight vector w1 uses both the x1 and y1, the weight vector w1 is available after consuming another computation time, which is assumed as being one snapshot period for easy explanation. The weight vector w1, which is multiplied by output y2 of pilot signal generating part (12), is used for channel compensation of symbol duration denoted by x31.

From above, it is analysed that channel output for duration of x1 is applied to x3 which is delayed two computation time. This result comes from condition that there are no butters between each block. If buffering blocks are used in this invention, even though time for obtaining result is delayed (when w1 is applied to x1 duration, time for channel compensation is delayed as two computation times is necessary), performance degradation due to two delay time can be avoided.

Processing means according to this invention can be implemented through software and recorded on recording medium (CD-ROM, ROM, RAM, floppy disk, hard disk, magnetic-optical disk, etc.) that can be read through computer program for implementing.

This invention takes an example of apparatus operating in CDMA2000 (called IS-2000 or IMT-2000) but it is clear that the finger disclosed in this invention can be applied to such as WCDMA. Also, the data rate of traffic channels is to help understand meaning of this invention and not confined to CDMA2000 system.

Optimum weight vector can be calculated by using the pilot signal in 3G mobile communication systems, because the traffic signal and the pilot signal are transmitted from mobile station. Mixed-rate weighting is possible because optimum weight vector using the pilot signal is applied to each traffic channel. If mixed-rate weighting is compared with other weighting method (for example, symbol-rate weighting or chip-rate weighting), mixed-rate weighting has following properties: In mixed-rate weighting, application speed of weight vector is reduced to chip-rate; another integration is not necessary as despreaded pilot signal is weighted when pilot signal is detected for channel estimation; and time difference between calculated weight vector and received signal applied into weight vector is one chip duration faster than chip-rate weighting.

According to this invention, interference can be reduced dramatically and capacity of communication be increased as weighting information is extracted from pilot channel which can have long integration interval. Furthermore, delay time necessary for signal processing can minimized and exact channel estimation is possible as mixed-rate weighting is used in demodulation apparatus. Also, performance of searcher and tracker can be enhanced when the phase diversity technology is used. Then, system performance is enhanced remarkably as exact phase compensation is accomplished by multiplying pilot signal received from array antenna with weight vector obtained from weight-vector computing part.

While the present invention has been described with respect to certain preferred embodiments, it will be apparent to those skilled in the art that various changes and modifications may be made without departing from the scope of the invention as defined in the following claims. 

1. A finger operating in mixed-rate, comprising: a descrambling means that descrambles received signals by multiplying a PN-code with the received signals using frame timing information; a pilot signal generating means that produces a pilot signal that is to be used as input of a weight vector computing means to compute a weight vector, by using a descrambled signal from the descrambling means, and finds out estimation value for delayed phase of each traffic channel; the weight vector computing means that produces the weight vector by using signals from the descrambling means and the pilot signal generating means; a general weighting means for producing a general weighted signal, by compensating phase delay of a base-band received signal with the weight vector; a pilot phase estimation means that produces phase compensation signal to compensate phase delay of each channel by using the weight vector and the pilot signal; a Walsh despreading means for providing received data for each of traffic channels, by using outputs of the general weighting means, the PN-code and corresponding Walsh codes; and a channel compensation means that compensates phase distortion caused by the phase delay to each output of the Walsh despreading means by using output of the pilot phase estimation means.
 2. The finger according to claim 1, further comprises a tracking means for producing frame tracking information for compensating small changes in path delay.
 3. The finger according to claim 2, wherein the tracking means produces the frame tracking information from difference between two energies which are obtained by integrating results of early and late descrambling wherein a first and a second synch time information are used, respectively.
 4. The finger according to claim 2, wherein the tracking means produces the frame tracking information from difference between two energies which are obtained by squaring weighted sums of integrations of descrambled signals provided through early and late descrambling wherein a first and a second synch time information are used, respectively.
 5. The finger according to claim 2, wherein the tracking means produces the frame tracking information from difference between two energies which are obtained by squaring results of integrations of weighted sums between the weight vector and descrambled signals provided through early and late descrambling wherein a first and a second synch time information are used, respectively.
 6. The finger according to claim 3, wherein the tracking means produces the frame tracking information from difference between two energies which are obtained by integrating results of the early and late descrambling wherein the first and the second synch time information are used, respectively, such the frame tracking information is produced after filtering the difference between the two energies.
 7. The finger according to claim 4, wherein the tracking means produces the frame tracking information from difference between two energies which are obtained by integrating results of the early and late descrambling wherein the first and the second synch time information are used, respectively, such the frame tracking information is produced after filtering the difference between the two energies.
 8. The finger according to claim 5, wherein the tracking means produces the frame tracking information from difference between two energies which are obtained by integrating results of the early and late descrambling wherein the first and the second synch time information are used, respectively, such the frame tracking information is produced after filtering the difference between the two energies.
 9. The finger according to claim 3, wherein the first synch time information for the early descrambling is earlier than the frame timing information by about 0.2 to 0.5 chip duration while the second synch time information for the late descrambling is later than the frame timing information by about 0.2 to 0.5 chip duration.
 10. The finger according to claim 4, wherein the first synch time information for the early descrambling is earlier than the frame timing information by about 0.2 to 0.5 chip duration while the second synch time information for the late descrambling is later than the frame timing information by about 0.2 to 0.5 chip duration.
 11. The finger according to claim 5, wherein the first synch time information for the early descrambling is earlier than the frame timing information by about 0.2 to 0.5 chip duration while the second synch time information for the late descrambling is later than the frame timing information by about 0.2 to 0.5 chip duration.
 12. The finger according to claim 1, wherein the descrambling means multiplies the received signal in digital state (I_rx, Q_rx) with a local PN-code using a finger timing information (f_timing) provided from outside finger.
 13. The finger according to claim 1, wherein the pilot signal generating means retrieves the pilot signal to be used as input of weight vector computing means by integrating output of the descrambling means for preset period of time.
 14. The finger according to claim 13, wherein the output of the pilot signal generating means and the descrambling means are denoted as y_vector signal and x_vector signal, respectively, and wherein the weight vector computing means produces the weight vector (Weight_I, Weight_Q) using the x_vector signal and the y_vector signal.
 15. The finger according to claim 14, wherein the weight vector computing means is reset to initial state upon reception of frame reset signal (f_reset) which is generated by finger death signal (f_death) when the PN-code acquisition is lost such that PN-code acquisition for lost path can be restarted with initial state.
 16. The finger according to claim 1, wherein the general weighting means produces an array output by multiplying the weight vector of chip-rate from the weight vector computing means with the descrambled signal (I_rx, Q_rx) and summing up results of multiplications.
 17. The finger according to claim 1, wherein the pilot phase estimation means produces a phase compensation signal to compensate phase delay of each traffic channel by multiplying the weight vector from the weight vector computing means with the pilot signal from the pilot signal generating means.
 18. The finger according to claim 1, wherein the Walsh despreading means includes: FCH (fundamental channel) despreading means for retrieving data transmitted through the FCH by descrambling an array output through multiplication of the array output with the PN-code and further multiplying result of the descrambling of the array output with the Walsh code corresponding to the FCH; DCCH (dedicated control channel) despreading means for retrieving data transmitted through DCCH by descrambling the array output through multiplication of the array output with the PN-code and further multiplying result of the descrambling of the array output with the Walsh code corresponding to the DCCH; SCH 1 (Supplemental channel 1) despreading means for retrieving data transmitted through SCH 1 by descrambling the array output through multiplication of the array output with the PN-code and further multiplying result of the descrambling of the array output with the Walsh code corresponding to the SCH 1; and SCH 2 (Supplemental channel 2) despreading means for retrieving data transmitted through SCH 2 by descrambling the array output through multiplication of the array output with the PN-code and further multiplying result of the descrambling of the array output with the Walsh code corresponding to the SCH
 2. 19. The finger according to claim 17, wherein the channel compensating means is located for compensating the phase distortion due to path delay associated with each of traffic channels the FCH, the DCCH, the SCH 1, and the SCH
 2. 20. The finger according to claim 2, wherein the tracking means, for providing exact chip synchronization through the fine-tuning of PN-code acquisition, includes: first complex descrambling means for multiplying the received signal with the PN-code of ½ chip advanced time to the f_timing; second complex descrambling means for multiplying the received signal with the PN-code of ½ chip retarded time to the f_timing; first and second energy estimation means for providing correlation energies by integrating results of first and second complex descrambling means, respectively; and tracking information (f_trk) generating means for providing the tracking information (f_trk) by comparing magnitudes of results of the first and second energy estimation means.
 21. A demodulation apparatus that uses fingers operating in mixed-rate for mobile communication system comprising: an analog-to-digital converter (ADC) for converting analog signal, which has been frequency-down converted to base-band, to corresponding digital signal through oversampling procedure; a searcher for transmitting correlation energy that exceeds preset threshold value to lock detector while the correlation energy is computed through correlation procedure between output of the ADC and a PN-code corresponding to a pilot channel; a lock detector for generating signals needed for accurate frame synchronization which are a frame reset (f_reset), a frame timing (f_timing), a frame death (f_death) information using the correlation energy provided from the searcher; and at least one finger wherein traffic channel signals are weighted in the mixed-rate with weights which are obtained from received data in the pilot channel of a reverse link.
 22. The demodulation apparatus according to claim 21, wherein each finger comprises: a descrambling means that descrambles base-band received signal by using frame time information; a pilot signal generating means that produces the pilot signal from the descrambling means and finds out estimation value for delayed phase of each traffic channel; a weight vector computing means that produces the weight vector using signals from the descrambling means and the pilot signal generating means; a general weighting means for producing an array output using the weight vector and the received signal; a pilot estimation means that produces phase compensation signal to compensate phase delay of each channel using the weight vector and the pilot signal; a Walsh despreading means that produces received data for each of the traffic channels, by using outputs of the general weighting means, the PN-code and corresponding Walsh codes; and a channel compensation means that compensates phase distortion caused by the phase delay to each output of the Walsh despreading means using output of pilot weighting means and traffic channels weighting means.
 23. The demodulation apparatus according to claim 22, wherein each finger further comprises a tracking means for producing frame tracking information produced from difference between two energies which are obtained by integrating results of early and late descrambling wherein first and second synch time information are used, respectively, in order to produce frame tracking information for compensating small changes in path delay.
 24. The demodulation apparatus according to claim 21, wherein the searcher comprises: a received signal processing means for achieving envelope detection of the received data such that the correlation energy to be obtained at each antenna channel; an adding means for summing up the correlation energies at each of antenna channels obtained from the received signal processing means; and an output means for generating result of the adding means as final output of non-coherent detection.
 25. The demodulation apparatus according to claim 24, wherein the received signal processing means comprises: first arithmetic means for computing magnitude of the correlation energy at each antenna channel by adding results of square of processing results along I-channel and Q-channel; and second arithmetic means for summing up results of computed magnitude of the correlation energy at each of antenna channels.
 26. A demodulation method using a finger that operates in mixed-rate for mobile communication system, comprising: a first step of descrambling received signal by multiplying a PN-code with a received signal using frame timing information (f_timing); a second step of generating a pilot signal obtained by integrating the descrambled signal in order to use the pilot signal for computing a weight vector; a third step of computing the weight vector by using the descrambled data and the pilot signal; a fourth step of generating an array output by summing up the results of multiplication between the weight vector and the received signal in such a way that inter-element phase difference be compensated; a fifth step of generating the phase compensating signal to compensate phase delay of channel by multiplying the weight vector with the pilot signal; a sixth step of generating received data for each traffic channel by using outputs of a general weighting step, the PN-code, and corresponding Walsh codes; and a seventh step of compensating a phase distortion due to the channel delay by using the phase compensation signal to weighted traffic signal.
 27. The demodulation method according to claim 26, wherein the fourth step, the weight vector is multiplied by the pilot signal after the pilot signal is exactly calculated through phase delay estimation.
 28. A computer-readable recording medium for recording a program that embodies a method using fingers operating in mixed-rate comprising: a first function of descrambling received signal by multiplying a PN-code with a received signal using frame timing information (f_timing); a second function of generating a pilot signal obtained by integrating a descrambled signal in order to use the pilot signal for computing weights; a third function of computing a weight vector using the descrambled signal and the pilot signal; a fourth function of generating an array output by summing up the results of multiplication between the weight vector and the received signal in such a way that inter-element phase difference be compensated; a fifth function of generating the phase compensation signal to compensate phase delay of channel by multiplying the weight vector with the pilot signal; a sixth function of generating received data for each traffic channel by using outputs of a general weighting step, the PN-code, and corresponding Walsh codes; and a seventh function of compensating a phase distortion due to the channel delay by using the phase compensation signal to weighted traffic signal. 